MILLIMETER WAVE PROPAGATION FOR IMPROVED DISTRIBUTED WIRELESS COMMUNICATION SYSTEMS

1
MILLIMETER WAVE PROPAGATION FOR IMPROVED DISTRIBUTED WIRELESS
COMMUNICATION SYSTEMS
BY
ELECHI PROMISE
(G2008/MENG/ELECT/FT/358)
DEPARTMENT OF ELECTRICAL/ELECTRONIC ENGINEERING
FACULTY OF ENGINEERING
SCHOOL OF GRADUATE STUDIES
UNIVERSITY OF PORTHARCOURT
PORTHARCOURT, NIGERIA
FEBRUARY, 2011

2
BY
ELECHI PROMISE
(G2008/MENG/ELECT/FT/358)
BEING A THESIS SUBMITTED TO THE DEPARTMENT OF
ELECTRICAL/ELECTRONIC ENGINEERING, IN PARTIAL FULFILMENT OF THE
REQUIREMENTS FOR THE AWARD OF MASTER’S DEGREE OF ENGINEERING
(M.ENG) IN ELECTRONIC AND TELECOMMUNICATION ENGINEERING, UNIVERSITY
OF PORTHARCOURT
FEBRUARY, 2011

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CERTIFICATION
UNIVERSITY OF PORTHARCOURT
SCHOOL OF GRADUATE STUDIES
BY
ELECHI PROMISE
G2008/MENG/ELECT/FT/358
DEPARTMENT OF ELECTRICAL/ELECTRONIC ENGINEERING
FACULTY OF ENGINEERING
THE BOARD OF EXAMINARS DECLARES AS FOLLOWS: THAT THIS IS THE
ORIGINAL WORK OF THE CANDIDATE. THAT THIS THESIS IS ACCEPTED IN
PARTIAL FULFILLMENT OF THE REQUIREMENTS FOR THE AWARD OF THE
MASTERS OF ENGINEERING
NAME SIGNATURE
SUPERVISOR ...................................... ........................
SUPERVISOR ...................................... ........................
HEAD OF DEPARTMENT ..................................... .........................
EXTERNAL EXAMINER ...................................... .........................
CHAIRMAN BOARD ....................................... .........................
OF EXAMINERS

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ABSTRACT
Millimeter wave propagation is envisioned to be a technology capable of delivering
high data rates in the presently dense spectral environment. In this thesis, extensive
measurements are conducted in a room environment at 60GHz to analyze channel
characteristics for various channel configurations. The channel parameters obtained
from measurements are analyzed based on generic channel models. A single-cluster
model is applied for various parameter retrieval and performance evaluations. On the
basis of this model, the power delay profiles are described by a root-mean-square delay
spread, K-factor and power delay profile. The channel is configured with various
combinations of omnidirectional, fan-beam and pencil-beam antennas at the receiver
and transmitter sides, at both line-of-sight and non line-of-sight conditions. Results
show that an increase in the signal coverage and performance can be achieved by
proper alignment of transmit and receive antenna beams within sight of one another.
Furthermore, performance under non line-of-sight conditions can be improved by the
use of directive antennas.

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DECLARATION
I hereby declare that this is my work and that it has not been submitted before
anywhere for the purpose of awarding a degree to the best of my knowledge.
Promise Elechi ........................... .................
Signature date

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DEDICATION
This work is dedicated to the Almighty God and to the memory of my late mother, Mrs.
Helen Chituru Elechi (Nee Orisa)

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ACKNOWLEDGEMENT
I use this opportunity to express my sincere gratitude to Almighty God who gave me the
strength to carry out this work.
My profound gratitude goes to Engr. (Dr.) Biebuma J.J. and Mr Eteng A., my thesis
supervisors for their personal commitments, sacrifices and words of wisdom which
contributed in no small measure to the realization of this thesis.
I equally thank Prof. A.O. Ibe, the postgraduate co-ordinator and Engr. (Dr.) Kamalu
Ugochukwu A., the head of the department of Electrical/Electronic Engineering and his
academic and non-academic staff for their encouragements.
I wish to thank my fiancée Miss Kate Chioma Amadi and my brothers and sisters
especially Miss Cynthia Obinichi, Mr. Alswell Kemjika Elechi, Miss Adanne Elechi, Miss
Faithful Elechi, Miss Rita Ebere Elechi, my cousin Mrs Elizabeth Chidi Nnwoka, my oga
Barrister Alwell Ezebunwo and my coursemates, Engrs. Armiyau Braimah, Igbekele
Omotayo and Saliu Mohammed for their kind assistance, encouragements, patience,
understanding and love during the programme.
Similar thanks goes to my parents, brothers and sisters and others for their
understanding and moral support.
I am indebted to the following staff of Daewoo Nigeria Limited, Bayelsa State, for their
numerous contributions towards the realization of my academic dream: Hezekiah
Kointeinbo-Ofori, Egeonu Innocent, S.Y. Lee, C.S. Kim, H.M. Kim, B.S. Oh, K.U. Bae,
J.K. Park, Nelson Tuotamuno, Peter Gogo Biekpo, John Ovie Eze and Kingsway
Nwuche.
Finally, I wish to specially thank Engr. and Mrs Nehemiah Chinenye, Ojadi my bosom
friends for standing by me throughout the academic period.

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TABLE OF CONTENT
Title page i
Certification iii
Abstract iv
Declaration v
Dedication vi
Acknowledgement vii
Table of Content viii
List of Figures x
List of Tables xiii
CHAPTER 1: INTRODUCTION 1
1.1 Background of Study 1
1.2 Statement of the problem 2
1.3 Objective of Study 2
1.4 Significance of Study 3
1.5 Scope of Study 4
CHAPTER 2: LITERATURE REVIEW 5
2.1 Historical review of wireless communication 5
2.2 Advantages of millimetre wave radio over ultra wideband technology.
6
2.3 Studies in millimetre wave radio technology 8
CHAPTER 3: METHODOLOGY 13
3.1 Description of the Experiment Environment. 13
3.2 Channel Model 20
3.3 Calculation 23
3.3.1 Received power 23
3.3.2 K-factor 24
3.3.3 Estimating the RMS delay spread from frequency-domain level crossing rate
25
3.3.4 Application to channel measurements 26
3.3.5 Power Delay Profile 28
CHAPTER 4: RESULTS AND DISCUSSION 29
4.1 Received Power 29
4.2 K-factor and Root Mean Square Delay Spread 44
4.3 Power Delay Profile 69
4.4 Maximum Excess Delays and Number of Multipath 74
Components
CHAPTER 5: CONCLUSION 75
5.1 Conclusion 75
5.2 Recommendation 76
REFERENCES 77
APPENDICES 79

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LIST OF FIGURES
Figure 3.1(a) and (b): HP8510C network analyzer 15
Figure 3.2: Plan view of the rooms 19
Figure 4.1:The received power over the travel distance of the first arrived path of
the omn. antenna (1.4/1.4) 30
Figure 4.2: The received power over the travel distance of the first arrived path of the
omn. Antenna (1.9/1.4) 31
omn. antenna(2.4/1.4) 32
omn antenna NLOS (1.4/1.4) 33
omn. antenna NLOS (1.9/1.4). 34
omn. antenna NLOS (2.4/1.4) 35
omn antenna for free space 36
Figure 4.8: The received power over the travel distance of the first arrived path for the
Fan-Omn antennas. 38
Fan-Fan antennas. 39
Fan-Pen antennas. 40
Fan-Fan (35°) 41
Fan-Pen (35°) 42
Figure 4.13: The K-factor over the travel distance of the first arrived path of the omn.
antenna (1.4/1.4). 44
antenna (1.9/1.4) 45
antenna (2.4/1.4) 46
antenna NLOS (1.4/1.4). 48
Figure 4.19: The K-factor over the travel distance of the first arrived path for the Fan-
Omn antennas. 51
Fan antenna. 52
Pen antennas. 53
Fan antennas with (35°) 54
Pen antennas with (35°) 55

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Figure 4.24: The RMS delay spread over the travel distance of the first arrived path of
the omn. antenna (1.4/1.4). 58
Figure 4.27: RMS delay spread over the travel distance of the first arrived path of the
omn. antenna NLOS(1.4/1.4). 61
Figure 4.30: RMS delay spread over the travel distance of the first arrived path for the
Fan-Omn antennas. 64
Fan-Fan antennas. 65
Fan-Pen antennas. 66
Figure 4.33: The RMS delay spread over the travel distance of the first arrived path for
the Fan-Fan antennas (35°) 67
Figure 4.34: The RMS delay spread over the travel distance of the first arrived path for
the Fan-Pen antennas (35°) 68
Figure 4.35: The Average power delay profiles shape for Fan-Pen antennas configuration
69
Figure 4.36: The Average power delay profiles shape for Fan-Pen antennas with 35°
misalignment configuration. 70
Figure 4.37: The Average power delay profiles shape for Omn-Omn configuration
71

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LIST OF TABLES
Table 3.1: Antenna parameters. 16
Table 3.2: Measurement configurations. 18
Table 4.1: Received power data under line of sight condition. 29
Table 4.2: Received power data under non line of sight condition. 33
Table 4.3: Received power data for free space 35
Table 4.4: Received power against distance for directive antennas37
Table 4.5: Received power against distance for directive antennas with 35° misalignment.
40
Table 4.6: K-factor against travel distance under LOS condition 44
Table 4.7: K-factor against travel for NLOS condition 47
Table 4.8: K-factor against travel distance for directive antennas. 51
Table 4.9: K-factor against distance for directive antenna with 35° misalignment
53
Table 4.10: RMS delay spread against distance under LOS condition
57
Table 4.11: RMS delay spread against distance under NLOS condition
60
Table 4.12: RMS delay spread against distance for directive antennas
63
Table 4.13: RMS delay spread against distance for directive antennas (35°)
66
Table 4.14: Normalized average PDP over Time delay 69
Table 4.15: The mean values of K, σ max, Bc, N and the log-distance model parameters
{PLo, n, Ώ} for various configurations.
73

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CHAPTER 1
INTRODUCTION
1.1 Background of Study
With the rapid progress in telecommunications, more and more
services are provided on the basis of broadband communications, such
as video services and high speed internet. The distributed wireless
communication system is a new architecture for a wireless access with
distributed antennas, distributed processors, and distributed controls.
With the worldwide construction of optical fiber-based backbone
networks providing almost unlimited communications capability, the
limited throughput of the subscribers loop becomes one of the most
stringent bottlenecks. Compared to the capacity of the backbone
network, which is measured by tens of gigabit per second, the
throughput of the subscriber loop is much lower, only up to hundreds
of megabits per second for wired systems (including fixed wireless
access).
However, Chong and Yong (2007), suggest that millimeter wave
technology can improve this low throughput of the subscribers loop.
Millimeter waves generally correspond to the electromagnetic spectrum
between 30GHz to 300GHz, with wavelengths between one and ten
millimeters. In the context of wireless communication, millimeter waves

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generally correspond to a few bands of spectrum near 30GHz, 60GHz
and 94GHz.
1.2 Statement of Problem
According to the Shannon capacity theorem:
(1)
where C is the channel capacity, B is the bandwidth and SNR is the
signal power to noise power ratio. An increase in bandwidth or signal
power to noise power ratio or both can improve the channel capacity
for a specific operating distance. But the basic hindrance to the
improvement of channel capacity by bandwidth adjustment is that
conventionally available spectrum is limited. This imposes a limit to the
achievable channel capacity improvement.
As Chong and Yong (op.cit) have suggested, the solution may lie in
the use of a different spectral window, albeit millimeter wave, to
achieve greater channel capacity. What is however not very clear, is the
suitability of millimeter waves for communication.
1.3 Objective of Study
The objective of this study is to analyze the channel
characteristics for various channel configurations of millimeter wave
transmissions at 60GHz. Specifically, this study will:

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(1) Experimentally determine channel parameters to describe the power
profiles, with which the 60GHz channel will be analyzed, and
consequently;
(2) Determine the most suitable antenna configuration for this channel.
1.4 Significance of Study
The power delay profile is a function characterizing the spread of
average received power as a function of delay; therefore it is important
to determine the time interval between transmission of a signal
through a communication channel and reception. The power delay
profile shows the maximum delay in a channel and so accounts for
the suitability of a channel. Its determination, in the context, would
provide insight into the capabilities of the 60GHz spectral window.
There are virtually no communications services operating in the
60GHz range. Therefore a successful implementation of the millimeter
wave scheme will be relatively interference free, and will pose no
interference to other existing technologies. The use of this spectral
window will make large amounts of bandwidth available for wireless
communication. Incorporating millimeter wave technology into
distributed wireless systems will remove the low throughput bottleneck
associated with the subscriber loops.

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1.5 Scope of Study
Although this study is geared towards obtaining a workable
channel configuration at 60GHz, this thesis does not consider the
effects of atmospheric oxygen, humidity, fog and rain within this
spectral window. Recent studies, however, show that the 60GHz
channel has negligible signal loss due to atmospheric oxygen – about
0.2dB/km (Lim et. al, 2007).

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CHAPTER 2
LITERATURE REVIEW
2.1 Historical Review of Wireless Communication
Wireless communications is not new; it has been around for
decades. Heinrich Hertz, Nikola Tesla, Gugliemo Marconi, and others
experimented with the transmission and reception of radio waves in the
19th century. The actual birth of radio occurred in 1890 when J.C.
Bose was experimenting with millimeter wave signals at just the time
when his contemporaries like Marconi were inventing radio
communications. In 1897, Marconi first demonstrated that radio
communication could provide wireless communication between ships
(Sadiku, 2002).
The development of wireless communications can be regarded as
taking place in three phases. The period spanning 1907 to 1945 can be
regarded as the pioneer phase. In 1907, Lee De Forest invented the
triode, which made possible the first amplitude modulation (AM)
scheme and the amplification of weak radio signals. Edwin Armstrong,
invented frequency modulation (FM) in 1935. World War II was a
stimulus to wireless communications, leading to the subsequent
development of consumer radio and television systems.

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The period spanning 1946 to 1968 can be considered as the initial
commercial phase, although the first regular commercial radio
broadcast began in 1920. The third phase began 1969. This phase
includes the beginning of cellular, mobile, satellite and personal
communication systems. The recent generation of cellular services use
Time Division Multiple Access (TDMA), Code Division Multiple Access
(CDMA), narrow-band Frequency Division Multiple Access (FDMA), and
Collision Sense Multiple Access (CSMA) spread spectrum (Pozar, 2001),
which are all mostly based on the principle of microwave propagation.
2.2 Advantages of Millimeter Wave Radio over Ultra
Wideband Technology.
It is a fact that the ultra-wideband (UWB) is also being used as a
means of improving channel capacity. But the 60GHz millimeter wave
band has the following advantages over it.
(1) The low emission and impulsive nature of UWB radio leads to
enhanced security in communication. UWB is able to deliver high-
speed multimedia wirelessly making it suitable for WPANs. However,
one of the most challenging issues for UWB is that international
coordination regarding the operating spectrum is difficult to achieve
and the IEEE standards are not accepted worldwide. This spectral
difficulty will deeply shape the landscape of WPANs in the future.

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Spectrum allocation is not an issue for 60GHz WPANs. This is one of
the reasons for 60GHz millimeter wave.
(2) Inter-system interference is another concern. The UWB band is
overlaid over the 2.4- and 5-GHz bands used for increasingly
deployed WLANs, thus the mutual interferences would be getting
worse and worse. According to Nan Guo, et al (2007), inter-system
interference problem exists in Europe and Japan. In order to protect
existing wireless systems operating in different regions, regulatory
bodies in these regions are working on their requirements for UWB
implementation. For the 60GHz band, worldwide harmonization is
possible but it is impossible for a regional UWB radio to work in
another region.
(3) Data-rate limitation is also a concern. Currently, the multiband
OFDM (MB-OFDM) UWB system can provide maximum data rate of
480MB/s which can only support compressed video. 60GHz can
easily go over 2GB/s such as in high definition multimedia interface
(HDMI).
(4) Variation of received signal strength over a given spectrum can be a
bothering factor. For the MB-OFDM UWB system, there are 5 band
groups covering a frequency range from 3.1GHz to 10.6GHz.
According to the Friis propagation rule, given the same transmitted

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power, propagation attenuation is inversely proportional to the
square of a group center frequency. If band group 1 can cover 10m,
coverage range for band group 5 is only 1.56m. On the other hand,
because of relatively smaller change in frequency, coverage range
does not change dynamically for the 60GHz radio.
2.3 Studies in Millimeter Wave Radio Technology
Yong and Chong, (2007) provide a generic overview of the current
status of the millimetre wave radio technology, in order to support the
multigigabit wireless applications. They envisioned that the 60GHz
radio will be one of the important candidates for the next generation
wireless systems as well as the role of antennas in establishing a
reliable communication link. Despite the many advantages offered and
high potentials application envisaged, the authors did not report on the
number of technical challenges and open issues that must be solved
prior to the successful deployment of this technology.
Nan Guo et al, (2007) extends the overview by summarizing some
recent works in the area of 60GHz radio system design. Some new
simulation results were reported which showed the impact of the phase
noise on bit-error rate (BER). The authors concluded that phase noise
is a very important factor when considering multigigabit wireless
transmission but did not offer any solution to averting the problem.

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Lim C.P. et al, (2007) proposed a 60GHz indoor propagation
channel model based on the ray-tracing method. The model is validated
with measurements conducted in indoor environment. The authors
highlighted important parameters such as root mean square (RMS)
delay spread and fading statistics in order to characterize the
behaviour of the millimeter wave multipath propagation channel
extracted from the environment database. The report was mostly based
on a ray-tracing method using spacing between 2GHz and 3GHz
continuous wave in the simulation.
Yang et al, (2007) used a different modeling approach in
characterizing the 60GHz propagation channel. A statistical-based
channel model was proposed based on the extensive measurements
campaign conducted in indoor office environment. Based on that, a
single-cluster power delay profile (PDP) was formed to best characterize
the channel statistics in which the PDP can be parameterized by K-
factor, RMS delay spread and shape parameter under both line-of-sight
(LOS) and non line-of-sight (NLOS) conditions. Various types of
antenna pattern were used but they could not solve the problem of
limited link budget due to high path loss during propagation in
distributed wireless communication.

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Kvicera and Grabner (2007), investigate the effect of rain
attenuation at 58GHz, based on the large measurement results
collected over a 5-year period. The measurement results obtained were
analysed and compared to the ITU-R recommendations which are valid
for estimating long-term statistics of rain attenuation for frequency up
to 40GHz. The reports are only important for point-to-point fixed
system up to 60GHz based on ITU-R recommendations.
Based on the report by Kvicera and Grabner (2007), Van der
Zanden et al, (2008), addresses the modelling and prediction of rain-
induced bistatic scattering at 60GHz. The factor is important as it
could cause link interference between 60GHz links when rain falls.
They showed that despite the high oxygen attenuation, coupling
between adjacent links caused by bistatic scattering could be
significant even in light rain as it affects distributed wireless
communication.
Mohammadi, et al (2007), proposed a direct conversion
modulator-demodulator for fixed wireless application. Though the
circuit is not for distributed wireless application but explains the basis
for wireless communication. The circuits consist of even harmonic
mixers (EHMs) realized with antiparallel diode pairs (APDPs), where
self-biased APDP is used in order to flatten the conversion loss of the

22
system versus local oscillator (LO) power. The impacts of the baseband
modulating signals (I/Q) imbalances and DC offsets on BER
performance of the system was also considered. A communication link
was built with the proposed modulator-demodulator and experimental
results showed that such a system can be a low-cost and high-
performance Quadrature Amplitude Modulation (16-QAM) transceiver
especially for the local multipoint distribution system (LMDS)
applications.
Tatu and Moldovan, (2007), proposed a practical circuit for the
60GHz radio. In the report, a V-band (the circuit is composed of four
90° hybrid couplers connected by 50Ώ microstrip transmission line)
receiver using an MHMIC multiport circuit was proposed. It was
demonstrated that the combination of multiport circuits with power
detectors and two different amplifiers can replace the conventional
mixer in a low-cost heterodyne or homodyne architecture. The
operating principle of the proposed heterodyne receiver and
demodulation results of high-speed multiport phase shift keying and
quadrature amplitude modulation (MPSK/QAM) signals were also
discussed. Simulation results showed that an improved overall gain
can be obtained. The authors concluded that such a multiport
heterodyne architecture can enable the compact and low-cost

23
millimetre-wave receivers for the future wireless communications
system.

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CHAPTER 3
METHODOLOGY
The method of study adopted in this work is to conduct
experiment to understand the behaviour of the channel of a distributed
wireless communication systems. The specific parameters to derive in
this experiment are: Root-mean-square delay spread, K-factor and
power delay profile shape, calculated from the measured received
power in describing the power delay profile. In the course of deriving
this parameters, the combination of omnidirectional antennas, fan-
beam antennas and pencil-beam antennas at the transmitter and
receiver are used in determining the most suitable antenna
configuration in both line-of-sight and non line-of-sight conditions. The
data obtained are interpreted as scatter diagrams showing the
maximum value of points in the analysis of each parameter. Subsection
3.2 shows the analytical relationship between the parameters as can be
obtained based on the experiment conducted in subsection 3.1.
3.1 Description of the Experiment Environment
Aim: The aim of this statistical measurement is to determine the
received power over certain distances, the K-factor which accounts for
fading, the root-mean-square delay spread and the power delay profile

25
which are used to analyze the channel characteristics for various
channel configurations.
Equipments Required: Two network analyzers (HP 8510C), two
Omnidirectional antennas, a Pencil-beam antenna and two Fan-beam
antennas, measurement tapes, Frequency generator and Angle
measurement indicator.
Procedure: The vector network analyzer (HP 8510C) was employed to
measure complex channel frequency responses as seen in figures 3.1
(a) and (b) used in rooms A and B respectively.
3.1(a)

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3.1(b)
Figures 3.1(a) and (b): HP8510C network analyzer
During measurements, the following steps were adopted to measure
the received power: Select the power in the measurement knob, adjust
the receiving antenna position, send a signal through the transmitting
antenna, and record the received power as well as the distance between
the transmitter and the receiver. Repeat for 20 measurements, after
which the transmitter height is adjusted by 0.5m and the steps are
repeated for three times, the step sweep mode was used and the sweep
time of each measurement was about 20 seconds. Channel impulse
responses were obtained by Fourier transforming the frequency
responses generated by the continuous wave frequency generator into
time domain after a Kaiser window was applied with a sidelobe level of
−44dB.
Note that in all the measurements, the transmit power is 0 dBm.

27
The Kaiser window is defined by the formula:
0 (3.1)
The Fourier transform of the Kaiser Window (where t is treated as
continuous) is:
(3.2)
where I0 is the modified Bessel function of the first kind of zero order.
Three types of vertical polarized antennas with different radiative
patterns, that is, omnidirectional, fan-beam, and pencil-beam
antennas, were applied in the measurements. Parameters of these
antennas, half power beamwidth (HPBW), and antenna gain, are listed
in Table 3.1.
Table 3.1: Antenna parameters.
Types of antennas Half power beamwidth (o) Gain (dBi)
E-plane H-plane
Fan beam 12.0 70.0 16.5
Pencil beam 8.3 8.3 24.4
Omnidirectional 9.0 omnidirectional 6.5
Two groups of measurements were conducted in room A and B
separately. Both rooms have a similar structure. The windows side
consists of window glasses with a metallic frame one meter above the

28
floor and a metallic heating radiator below the window. The concrete
walls are smoothly plastered and the concrete floor is covered with
linoleum. The ceiling consists of aluminium plates and light holders.
Some large metallic objects, such as cabinets, were standing on the
ground. Note that in room A, three aligned metallic cabinets are
standing in the middle of the room and two metallic cable boxes with a
height of 3.2m are attached to the brick wall side 2. The space between
cabinets and ceiling were blocked by aluminium foil for the ease of the
measurement analysis. Figure 3.2 shows the plan of rooms A and B.
Table 3.2 lists the measurement system configurations and
scenarios. In room A, at both the transmitter and the receiver side, the
same type of omnidirectional antennas was used. Three height
differences of TX-RX were considered, namely, 0.0, 0.5, and 1.0m
(denoted by OO0.0, OO0.5, and OO1.0 for three cases, respectively.). Both
line-of-sight and non-line-of-sight (NLOS) channels were measured in
room A.

29
Table 3.2: Measurement configurations.
Room Frequency range (GHz) Antenna (TX/RX)
TX RX Height (m)
A 57-63 Omn Omn 1.4/1.4 OO0.0
1.9/1.4 OO0.5
2.4/1.4 OO1.0
B 58-62 Fan Omn 2.5/1.4 FO
Fan 2.5/1.4 FF,FF±35
Pen 2.5/1.4 FP,FP±35
In room B, a sectoral horn antenna with fan-beam pattern was applied
at the transmitter side and located in a corner of the room at the height
of 2.5m. At the receiver side, three types of antennas with
omnidirectional, fan-beam, and pencil-beam patterns at the height of
1.4m were used. The three TX/RX combinations are denoted by FO,
FF, and FP, respectively, in which of the latter two cases the TX/RX
beams are directed towards each other. In addition, the channels were
measured for the cases of FF and FP with TX/RX beams misaligned by
±35◦ (denoted by FF±35◦ and FP±35◦ ). In room B, only LOS channels were
measured.
During measurement, there were no movement of persons in the
rooms so as to minimize Doppler Effect.

30
11.2m
Brick wall side
1
VNA 0.2 x 0.1 x 2m3
0.6 x 0.8 x 1.6m
3
TX
6 x 0.1 x 1m
3
Wooden table
Concrete wall
(0.15+0.35) x 0.1 x 3.2m3
3.2
Concrete pillar
3.9m Brick wall side
3,4 4
2.5m
Door
Metalliccabinets
1x0.4x3.2m3
Windows
side
6m
Metallic object
Brick wall side 2
1 X 0.4 X 2m
3
1 X 0.4 X 2m
3
7.2m
Side 1
Side4
Equipme
nt
Side2
1.5m
6m
1 X 0.4 X 2m3Door
Metallic object
Side 3
(b) Room B
Figure 3.2: Plan View of the rooms.
TX
(a) Room A

31
3.2 Channel Model.
Assuming the channel statistic is stationary or quasi-static, as in
a physical channel, that is, wide sense stationary (WSS) within the time
duration of one transmitted symbol or data package; signals from
different paths will experience uncorrelated attenuation, phase shifts
and time delay, referred to as uncorrelated scattering (US). The wide
sense stationary uncorrelated scattering (WSSUS) condition for
physical channels has been experimentally confirmed and widely
accepted (Moraitis and Constantiou, 2004). On this basis, the
autocorrelation of the complex impulse response will be only
dependent on the time difference and satisfies:
 
   2
2
2
1
*
21
*
21
,(),(
,(),(
),;(



tthEthE
tththE
th



= )(),( 121  th (3.2.1)
From the first principle of wave propagation, the reduction of wave
propagation to its fundamental properties, and the reduction of the
environment to its key geometrical quantities allow the analytical
determination of the power delay profile in a single room environment.
In a single room environment, the reflected wave depends on the room
size, the wall and ceiling materials. Each image source n is supposed to
n
to reach the Receiver. Each pulse is reflected n times at the wall and

32
ceiling of the room. The average power delay profile of the channel can
be defined as the autocorrelation function when t = 0 (eq. 3.2.1).
P     )(),()( 2
0
2
nn
N
n
EthE   
(3.2.2)
Equation (3.2.2) is the average of the instantaneous power delay
profiles in a local area. From the average power delay profile, the Root
mean square delay spread, σs can be defined by
22
0
)()(   
nn
N
n
S E (3.2.3)
Where  is the mean excess delay
Assuming   12
0

n
N
n
E 
Then,  = ).(
0
nn
N
n
P 
Root mean square delay spread (RDS) is generally used to characterize
the time dispersion of the channel.
From the equation of the complex lowpass impulse response of a Rician
channel; the equivalent complex channel frequency response can be
),( th 

N
n
nn
j
n
j
tt
1
000 )()()()(  
The Fourier transform is defined as:
`)()( dttff jwt
 

33




 
N
n
jw
n
tj
n
jw
o
tj
o ddf no
1
)()(
)()()(  

 




 
N
n
jw
n
tj
n
jw
o
tj
o dd no
1
)()(
))(()(  





 
N
n
n
jwtj
no
jtj
o dd no
1
)()(
)()(  

Using the sampling property of the impulse function:
)()()( oo
b
a tfdttttf  



N
n
jwtj
n
jwtj
o
nnoo
1
)()( 
 



N
n
wtj
n
wtj
o
nnoo
1
))(())(( 
 



N
n
wtj
n
nn
0
))(( 
 
But, f 2


N
n
ftj
n
nn
0
)2)(( 
 
H 

N
n
nn
j
n ftft
0
)2)((),(   (3.2.4)
Equation (3.2.4) is the equivalent channel frequency response of a
wireless communication system, indicating that it decays exponentially
over time delay. Under the WSSUS assumption, the frequency auto
correlation function of does not depend on the specific frequency
and can be written as:

34
 
   2
2
2
1
*
21
*
21
),(),(
),(),(
),(
fttHEftHE
fttHftHE
fftjH



= ),( ftH  (3.2.5)
Where f = f2 - f1
At t = 0, equation (3.2.5) becomes H (0, f) which represents the
channel coherence level over the frequency separation f. The
coherence bandwidth, Bc is defined as the largest frequency separation
over which the correlation | )( fH  is not smaller than a level. The
coherence bandwidth is a statistical measure in characterizing the
frequency selectivity of the channel. Due to Doppler Effect caused by
moving objects or moving antennas at the transmitter or receiver side,
the transmission channel can vary over time which results in a
spectrum broadening.
3.3 Calculation
3.3.1 Received Power
In this thesis, the free space propagation is used in predicting the
received signal strength when the transmitter and receiver have a clear
line-of sight path between them. The receiving antenna is separated
from the transmitting antenna in free space by distance, r.
The power received, Pr by the receiving antenna is given by the Friis
equation:

35
(3.3.1)
Where Pt is the transmitted power, Gr is the receiving antenna gain, Gt
is the transmitting antenna gain and λ is the wavelength of the
transmitted signal.
λ = (3.3.2)
where C = 3 108 and
Equation 3.3.1 is commonly expressed in logarithmic form and if all
the terms are expressed in decibels (dB). Equation 3.3.1 can be written
in the logarithmic form as:
(3.3.3)
Where P is the power in dB, G is gain in dB and Lo is the free space loss in
dB.
The free space path loss is obtained directly from equation 3.3.1 as
(3.3.4)
3.3.2 K-Factor
The K-factor is the ratio of the powers contributed by the steady
path to the scattered path. The power contributed by the dominant
path is derived by adding the powers within the resolution bin of the
dominant path and is known as the steady path power. The mean of
the transmitted powers outside the resolution bin is known as the

36
scattered path power. The K-factor is calculated for each measurement
in 3.1 using the formula below.
To ensure that there is less fading in the channel, the K-factor must be
greater than 8 (K ).
3.3.3 Estimating the Root-Mean-Square Delay Spread from
Frequency-Domain Level Crossing Rate
The root-mean-square (RMS) delay spread is probably the most
important single measure for the delay time extent of a multipath radio
channel (Witrisal, et al, 1998). Since the impulse response (IR) and the
transfer function (TF) of a channel are related by the Fourier transform,
it is intuitively understandable that the transfer function's magnitude
shows more fades per bandwidth. There exists a well-defined
relationship between the so-called level crossing rate in the frequency-
domain and the RMS delay spread (Rrms), written as:
(3.3.5)
As seen from this equation, Rrms and the LCRf are proportional, where
the proportionality factor is a function of:
(1) the Rician K-factor, K

37
(2) the threshold value at which the LCRf is determined, r' (r' is
normalized to the RMS amplitude value of the transfer function)
(3) and the channel model, expressed by u. (This influence is very small,
therefore it can be neglected.)
For the LCRf at the RMS amplitude value of the channel transfer
function, the factor, can be approximated by
(3.3.6)
3.3.4 Application to Channel Measurements
Equation (3.3.8) allows for the estimation of a complete set of wide-
band channel parameters (average received power, Rician K-factor, and
RMS delay spread) from rather simple swept-frequency power
measurements of the channel. (Note that the Fourier transform cannot
be used to calculate an impulse response from a measured power
response, due to lack of phase information). The following
measurement procedure is adopted in this thesis:
(1) Measure the narrowband power (or magnitude) response of the
channel as a function of frequency. (A continuous wave frequency
generator and the spectrum analyzer (HP 8510C) was used to conduct
the measurements).

38
(2) Calculate the average received power and the Rician K-factor from the
measured power response.
(3) Count the number of level crossings at a specific threshold, preferably
at the RMS amplitude.
(4) Use equation (3.3.8) for estimating .
An observation bandwidth of 10/Rrms (equivalent to the observation of
approximately 20 level crossings) was allowed for estimating Rrms at
accuracy in the order of 10%. Higher bandwidths can enhance the
accuracy. Alternatively, multiple measurements from within a small
local area such as this measurement rooms can be combined to
increase the observation bandwidth without modifying the
measurement equipment.
Other issues that were considered when applying this method for
channel investigations are:
(1) Influence of the sampling interval of the channel's frequency response:
The sampling interval was selected according to the sampling
theorem; otherwise some fades may be missed when counting the
level crossings.
(2) Influence of measurement equipment noise: Noise may introduce
additional level crossings, which would lead to over estimation of Rrms.

39
The sampling interval mentioned above should be as large as possible
to minimize this noise effect.
3.3.5 Power Delay Profile
The received power over time delay for each measurement in 3.1
accounts for the power delay profile of the channel. For each
transmitted signal, the received power is recorded and divided by the
time delay of the signal to reach the receiver.
(3.3.7)
where PDP is the power delay profile, Pri is the ith received power and
i is the ith time delay.

40
CHAPTER 4
RESULTS AND DISSCUSION
4.1 Received Power
The tables below show the data obtained in the measurements carried
out, and are used in the graphical analysis of the parameters using
scatter diagrams to determine the maximum value in analyzing the
behaviour of the various parameters under different configurations.
Table 4.1: Received power data under line of sight condition.
Received
Power(dBm)
Distance(m)
(1.4/1.4)
Received
Power(dBm)
Distance(m)
(1.9/1.4)
Received
Power(dBm)
Distance(m)
(2.4/1.4)
-48 0.9 -67 0.9 -70 1.2
-48.5 0.1 -68 1.1 -72 1.3
-50 1.2 -64.4 1.2 -72.5 1.2
-50 1.3 -65.5 1.5 -74 1.3
-51 1.5 -66 1.45 -75 1.8
-52 1.53 -64 1.8 -71 2.0
-51 1.8 -64 2.1 -71.5 2.1
-53 2.2 -63 2.0 -71 2.0
-53 2.3 -66 1.9 -73 3.2
-54 2.1 -67 2.1 -71 3.4
-54 2.7 -67.5 2.2 -71 3.6
-55 2.0 -65 2.7 -69 3.9
-55 3.0 -66 2.9 -72 4.0
-56 4.4 -66 3.0 -71 4.1
-56 3.2 -66.5 3.3 -75 3.2
-57 2.6 -65 3.2 -75 3.3
-58 1.4 -70 3.5 -74 5.4
-60 4.2 -65 3.5 -74 5.5
-61 1.8 -68 5.3 -74 5.6
-62 3.7 -65 2.2 -74 6.5

41
Figure 4.1:The received power over the travel distance of the first arrived
path of the omnidirectional antenna at heights(1.4/1.4).
0 0.5 1 1.5 2 2.5 3 3.5 4 4.5
-62
-60
-58
-56
-54
-52
-50
-48
Travel distance of the first arrived path for omn-omm (m)(1.4/1/4
ReceivedPower(dBm) received power(dBm)against travel distance

42
Figure 4.2: The received power over the travel distance of the first
arrived path of the omnidirectional antenna at heights (1.9/1.4).
0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
-70
-69
-68
-67
-66
-65
-64
-63
Travel distance of the first arrived path for omn-omm(1.9/1.4)
ReceivedPower(dBm)
Received power (dBm) against travel distance under LOS condition

43
Figure 4.3: The received power over the travel distance of the first arrived
path of the omnidirectional antenna at heights (2.4/1.4).
Note that the x-axis of each plot is the travel distance of the first
arrived wave, that is, the direct wave for the LOS case and the first
reflected wave for the NLOS case. Figure 4.1 has a maximum received
power of -48dBm while figures 4.2 and 4.3 has maximum received
powers of -63dBm and -69dBm respectively. The results show that as
the transmitter height is increased against the receiver, the received
power decreases. It therefore means that when the antennas are
properly aligned within the sight of each other, the received power is
maximum compared to when the heights are at variance to each other.
1 2 3 4 5 6 7
-75
-74
-73
-72
-71
-70
-69
ReceivedPower(dBm)
Received power (dBm) against Travel distance (m) under LOS condition

44
Table 4.2: Received power data under non line of sight condition
path of the omnidirectional antenna under NLOS at heights (1.4/1.4).
8 9 10 11 12 13 14
-80
-75
-70
-65
-60
-55
ReceivedPower(dBm)
Received power (dBm) against travel distance under NLOS condition
Received
Power(dBm)
Distance(m)
1.4/1.4
Received
Power(dBm)
Distance(m)
(1.9/1.4)
Received
Power(dBm)
Distance(m)
(2.4/1.4)
-56 8.5 -66 8 -70 8
-60 8.1 -66 8.5 -73 7.8
-63 8.0 -69 8.2 -70 7.8
-66 8.0 -70 9.0 -83 10
-60 8.2 -71 9.1 -82 9.5
-64 8.5 -71 8.9 -83 10.5
-64 8.7 -72 9.0 -83 11
-67 8.5 -71 8.9 -84 12
-66 9.8 -68 11.5 -84 12.3
-67 9.3 -70 11.3 -84 12.8
-68 9.1 -71 11.5 -83 13
-72 9.5 -75 13.3 -76 10
-73 9.4 -75 12 -74 10.5
-75 9.2 -80 13.6 -72 11
-72 12.5 -76 13.0 -80 13
-77 13.5 -83 11.5 -81 12.6
-71 12 -80 12 -80 13.5
-63 11 -83 13 -79 13
-67 10.5 -73 10.5 -73 11.5
-67 11.5 -72 11 -74 10.8

45
8 9 10 11 12 13 14
-84
-82
-80
-78
-76
-74
-72
-70
-68
-66
ReceivedPower(dBm)
Received power (dBm) against travel distance under NLOS condition

46
Table 4.3: Received power data for free space
Received
Power(dBm)
-30 -33 -35 -37 -40 -40 -43 -45 -47 -50 -53 -55 -57 -60 -67 -65 -67 -70 -73 -77
Distance(m) 1.9 2.0 2.2 2.4 2.5 2.3 2.5 4.3 3.0 3.3 3.4 3.5 4.0 5.7 4.8 5.0 5.2 7 10 14
7 8 9 10 11 12 13 14
-84
-82
-80
-78
-76
-74
-72
-70
ReceivedPower(dBm) Received power (dBm) against travel distance under NLOS condition

47
path of the omnidirectional antenna under free space condition.
0 2 4 6 8 10 12 14
-75
-70
-65
-60
-55
-50
-45
-40
-35
-30
Travel distance of the first path.
ReceivedPower(dBm) Received power (dBm) against travel distance under free space

48
In the non line-of-sight condition, the travel distance of the first arrived
path, is almost twice the travel distance of the line-of-sight condition
and with a reduced received power. Figure 4.4 shows a maximum
received power of -56dBm and a reduction as the distance is increased.
Figures 4.5 and 4.6 showed that as the transmitter height is increased,
the received power decreased to -66dBm and -70dBm respectively. In
figure 4.7, the free space curve gives the accurate data for the
omnidirectional configuration due to the highly reflective environment.
Since the transmission must get to a target destination (receiver), the
free space is not ideal, considering the objective of this thesis.
Table 4.4: Received power against distance for directive antennas
Received
Power(dBm)
Distance(m)
Fan-Omn
Received
Power(dBm)
Distance(m)
Fan-Fan
Received
Power(dBm)
Distance(m)
Fan-Pen
-65 1.9 -49 1.9 -40 1.9
-66 2.0 -46 2.0 -39 2.1
-65 2.2 -47 2.1 -40 2.2
-63 2.4 -48 2.2 -41 2.3
-60 2.5 -47 2.3 -41 2.4
-62 2.3 -46 2.5 -41 2.5
-64 2.5 -45 2.5 -41 2.6
-65 4.3 -44 2.6 -39 2.7
-66 3.0 -43 2.7 -38 2.8
-53 3.3 -43 2.8 -37 2.9
-56 3.4 -44 2.9 -36 3.0
-58 3.5 -42 3.0 -35 3.1
-57 4.0 -42 3.1 -34 3.2
-60 5.7 -42 3.2 -34 3.3
-57 4.8 -42 3.3 -34 3.4
-58 5.0 -42 3.5 -34 3.5
-59 5.2 -41 3.6 -34 3.6
-58 4.3 -41 3.8 -33 3.7
-57 4.2 -41 4.0 -33 3.8
-59 5.2 -42 4.2 -34 3.9

49
path for the Fan-Omn antennas.
1.5 2 2.5 3 3.5 4 4.5 5 5.5 6
-66
-64
-62
-60
-58
-56
-54
-52
Travel distance of the first arrived path for the directive antenna(m)
ReceivedPower(dBm) Received power against TX/RXdistance for Fan-Omn antennas

50
path for the Fan-Fan antennas.
1.5 2 2.5 3 3.5 4 4.5
-49
-48
-47
-46
-45
-44
-43
-42
-41
ReceivedPower(dBm) Received power against TX/RXdistance for Fan-Fan antennas

51
path for the Fan-Pen antennas.
Table 4.5: Received power against distance for directive antennas with 35°
Received
Power(dBm)
-53 -51 -50 -53 -53 -54 -53 -54 -50 -49 -48 -48 -48 -49 -48 -49 -47 -47 -47 -47
Distance(m)
Fan-Fan 35°
1.9 2.0 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3.1 3.2 3.3 3.4 3.5 3.6 3.7 4.2 4.4
Received
Power(dBm)
-66 -67 -67 -68 -65 -64 -64 -65 -65 -65 -65 -66 -66 -67 -65 -66 -66 -65 -66 -65
Distance(m)
Fan-Pen 35°
1.9 2.0 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.9 3.0 3.2 3.3 3.5 3.6 3.7 4.2 4.3 4.4 4.5
1.5 2 2.5 3 3.5 4
-41
-40
-39
-38
-37
-36
-35
-34
-33
ReceivedPower(dBm) Received power against TX/RXdistance for Fan-Pen antennas

52
path for the Fan-Fan antennas with 35° misalignment.
1.5 2 2.5 3 3.5 4 4.5
-54
-53
-52
-51
-50
-49
-48
-47
Travel distance of the first arrived path for directive antenna(m)
ReceivedPower(dBm) Received power against TX/RXdistance for Fan-Fan 35(degree) deviation

53
path for the Fan-Pen antennas with 35° misalignment.
1.5 2 2.5 3 3.5 4 4.5
-68
-67.5
-67
-66.5
-66
-65.5
-65
-64.5
-64
Travel distance of the first arrived path for directive antenna(m)
ReceivedPower(dBm)
Received power against TX/RXdistance for Fan-Pen 35(degree) deviation

54
Figure 4.8 has a maximum received power of -53dBm and
compared to the directive antenna configuration in figures 4.9 to 4.12,
the power level is much higher and the scattered points strongly
assume a definite path except those close to the transmitter that are
very sensitive to the unintentional beam pointing errors. This is due to
the use of an omnidirectional antenna as the receiver. When the
receiver beams are misaligned intentionally by ±35˚ over the boresight,
the received power by the fan-pen configuration (figure 4.10) will drop
about 27dB due to narrower antenna beam, compared to the 5dB drop
by the fan-fan antennas as shown in figure 4.9. From observations, the
35˚ misalignment is about half the beamwidth of the fan-beam antenna
and thus the direct path is still within the sight. It appears that the
loss exponents are much smaller than the free-space exponent for the
omn-omn configurations but approximately equal to 2 for the directive
antenna loss exponent.

55
4.2 K-Factor and Root Mean Square Delay Spread
Table 4.6: K-factor against travel distance under LOS condition
K-factor Distance(m)
1.4/1.4
1.9/1.4
2.4/1.4
2.1 0.8 0.3 0.9 0.1 1.2
1.2 1.0 0.2 1.0 0.3 1.3
1.8 1.0 0.4 0.8 0.5 1.0
0.4 2.0 0.6 1.3 0.2 1.8
1.0 2.3 1.8 1.2 0.1 1.9
1.1 2.4 1.7 1.8 0.4 2.1
1.2 3.0 0.4 2.1 0.5 2.2
1.4 4.2 0.5 2.0 0.3 2.3
1.6 4.1 0.5 2.1 0.1 2.5
1.8 4.3 0.7 3.0 0.2 2.1
0.9 4.2 0.5 3.3 0.4 2.2
1.0 4.2 0.3 3.4 1.0 2.4
1.0 4.5 0.5 4.2 0.9 2.3
1.2 4.2 0.1 4.5 0.7 2.5
1.3 3.3 1.0 4.3 1.0 3.4
1.4 3.4 1.1 4.2 0.8 3.3
1.6 3.2 1.0 4.3 0.4 3.2
1.5 1.0 0.7 4.2 0.1 4.3
1.8 3.4 0.9 5.0 0.2 5.2
1.3 5.0 0.6 5.2 0.5 5.3
Figure 4.13: The K-factor over the travel distance of the first arrived
path of the omnidirectional antenna at height (1.4/1.4).
0.5 1 1.5 2 2.5 3 3.5 4 4.5 5
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
2
2.2
2.4
K-factor
Travel distance of the first arrived path for omnidirectional antenna(m)(1.4/1.4)
K-factor against travel distance under LOS condition

56
Figure 4.14: The K-factor over the travel distance of the first arrived path of
the omnidirectional antenna at heights (1.9/1.4)
0.5 1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
0
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
K-factor
Travel distance of the first arrived path for omnidirectional antenna(m)(1.9/1.4)

57
the omnidirectional antenna at heights (2.4/1.4)
Figures 4.13 to 4.23 shows the instantaneous K-factors and the
travel distance of the first arrived path. When calculating the K-factor,
the power contributed by the dominant path is derived by adding up
the powers within the resolution bin of the dominant path. The root
mean square delay spread is calculated from the delay profile with a
dynamic range fixed at 30dB. Figure 4.13 shows a maximum K-factor
of 2.1, indicating that there is high mean value of the scattered path
power signals in the channel and in figures 4.14 and 4.15, K is less
than 1, despite the increase in the transmitter height and condition of
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1K-factor
Travel distance of the first arrived path for omn-omn(m)(2.4/1.4)

58
measurement. In figure 4.18, it increased to 5.4, but it cannot be said
that the channel is free from fading. In figure 4.17 below, the maximum
K-factor is 8.9, but most of the points lie between 1 and 3 indicating
that, that configuration can only be used when the travel distance is
between 8 and 9. This means that in non line of sight condition, the
receiver must be stationary else more fading will be introduced into the
communication channel.
Table 4.7: K-factor against travel for NLOS condition
1.4/1.4
1.9/1.4
K-factor Distance
2.4/1.4
4.8 8.0 7.4 8.9 5.3 8.3
2.0 7.8 7.2 8.1 0.5 8.6
2.1 8.4 8.9 8.7 1.2 9.1
1.9 8.2 4.9 9.1 0.3 9.3
1.5 8.1 2.1 9.3 0.4 8.4
1.8 8.5 2.3 9.4 0.3 10.3
1.7 8.6 1.8 10.4 0.2 10.6
1.9 9.2 1.9 11.0 0.3 11.0
1.5 9.3 2.0 10.8 0.4 10.4
1.8 9.0 1.5 10.7 0.3 8.4
0.1 10.4 1.3 11.4 0.5 8.6
0.4 10.3 2.1 12.4 1.2 10.4
0.3 11.2 2.0 12.5 1.3 13.0
0.2 12.3 2.3 13.0 1.5 13.3
0.5 11.4 2.4 9.4 0.3 12.1
0.4 11.4 2.6 9.6 0.6 12.3
0.3 11.6 2.8 12.4 1.3 8.6
0.2 12.4 1.0 13.0 2.1 8.4
0.3 13.3 1.1 13,3 2.3 9.3
1.8 13.5 1.3 13.3 3.5 9.4

59
the omnidirectional antenna under NLOS condition at heights (1.4/1.4).
7 8 9 10 11 12 13 14
0
1
2
3
4
5K-factor
Traveldistanceofthefirst arrivedpathforomn-omnantennas(m)(1.4/1.4)
k-factoragainst traveldistanceunderNLOS condition

60
the omnidirectional antenna under NLOS condition at heights (1.9/1.4)
8 9 10 11 12 13 14
1
2
3
4
5
6
7
8
9K-factor
Travel distanceofthefirst arrivedpathforomn-omnantennas(m)(1.9/1.4)
K-factoragainst travel distanceunderNLOS condition

61
Figure 4.18: The K-factor over the travel distance of the first arrived
path of the omnidirectional antenna under NLOS condition at heights
(2.4/1.4).
8 9 10 11 12 13 14
0
1
2
3
4
5
6
K-factor
Travel distance of the first arrived path for omn-omn antennas(m)(2.4/1.4)
K-factor against travel distance under NLOS condition

62
Table 4.8: K-factor against travel distance for directive antennas
Fan-Omn
Fan-Fan
Fan-Pen
0.8 1.9 10.0 1.9 11.0 1.9
1.0 2.0 11.0 2.0 12.0 2.0
1.0 2.2 10.0 2.3 15.0 2.2
1.2 2.3 13.0 2.3 18.0 2.4
1.5 2.5 12.0 3.4 16.0 3.4
1.4 3.0 14.0 3.0 20.0 3.2
1.6 2.8 15.0 3.1 21.0 3.3
1.8 3.4 14.0 3.2 23.0 4.6
2.1 3.6 16.0 3.4 36.0 4.2
2.3 3.7 12.0 4.0 20.0 4.8
1.3 3.5 11.0 4.2 21.0 3.4
1.5 3.6 10.0 4.4 18.0 5.3
5.0 4.0 9.0 4.3 19.0 5.2
4.3 4.2 8.0 5.0 24.0 4.8
4.8 4.3 7.0 5.3 16.0 4.6
3.0 4.2 10.0 5.4 12.0 3.6
3.5 4.6 12.0 5.6 11.0 4.8
3.6 5.0 13.0 4.3 10.0 5.0
4.0 5.4 11.0 4.2 13.0 5.3
2.0 5.3 13.0 4.1 14.0 5.2
Figure 4.19: The K-factor over the travel distance of the first arrived path
for the Fan-Omn antennas.
1.5 2 2.5 3 3.5 4 4.5 5 5.5
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
Travel distance of the first arrived path for Fan-omn antennas(m)
K-factor
K-factor against TX/RX distance

63
for the Fan-Fan antennas antenna.
1.5 2 2.5 3 3.5 4 4.5 5 5.5 6
7
8
9
10
11
12
13
14
15
16
Travel distance of the first arrived path for Fan-Fan antennas(m)
K-factor K-factor against TX/RXdistance

64
for the Fan-Pen antennas.
Table 4.9: K-factor against distance for directive antenna with 35°
K-factor Distance(m) for Fan-Fan K-factor Distance(m) for Fan-Pen
8 1.9 4 1.9
10 2.0 1 2.0
9 2.2 2 2.3
8 2.4 4 2.4
10 3.4 5 2.0
7 3.2 6 3.0
8 3.3 1 3.4
10 4.6 3 4.6
6 4.2 4 4.1
7 4.8 5 4.3
8 3.4 7 5.0
10 5.3 2 5.2
11 5.2 4 5.3
12 4.8 6 4.3
11 4.6 3 4.4
6 3.6 2 4.6
7 4.8 5 4.1
8 5.0 4 4.3
10 5.3 3 4.2
20 5.2 4 5.0
1.5 2 2.5 3 3.5 4 4.5 5 5.5
10
15
20
25
30
35
40
Travel distance of the first arrived path for Fan-Pen antennas(m)
K-factor
K-factor against TX/RX distance

65
for the Fan-Fan antennas with 35° misalignment.
1.5 2 2.5 3 3.5 4 4.5 5 5.5 6
6
8
10
12
14
16
18
20
Travel distance of the first arrived path for Fan-Fan antennas(m)
K-factor
K-factor against TX/RXdistance with 35(degrees) deviation

66
for the Fan-Pen antennas with 35° misalignment.
For the directive antenna configurations of fan-fan and fan-pen,
as the result of the significant suppression of multipath waves, it is
observed that most of the channel parameters are in the region of K >
10, σ < 1.5ns, Bc0.5 > 400MHZ, and Bc0.9 > 40MHz. where Bc0.5 and Bc0.9
are the coherence bandwidths at the correlation levels 0.5 and 0.9
1.5 2 2.5 3 3.5 4 4.5 5 5.5
10
15
20
25
30
35
40
K-factor
K-factor against TX/RX distance with 35(degrees) diviation

67
respectively, the mean values are listed in table 4.15. The mean values
are obtained by taking the various points of each of the parameters
obtained, and can be computed using the formular below.
(4.1)
where N is the total number of values of each parameter, is the mean
value of each parameter, is the various values of the parameters from
i to N.
When the transmitter and receiver beams are not pointing to each
other, the beam-pointing errors, for instance the 35˚ -misalignment for
the Fan-Pen configuration can seriously worsen the channel condition
in terms of large root mean square delay spreads (RDSs), and the
enormous drop of received powers, K-factors and coherence bandwidth.
This implies that channel configurations with wider beams are less
sensitive to beam-pointing errors. That means, the width of the beam
has to be properly designed to prevent an enormous drop of channel
quality caused by beam-pointing errors. In practice, multiple antennas
can be deployed and beamforming algorithms will be used to achieve
higher gain and suppress multipath effect by steering the main beam
to the direction of the strongest path. Figures 4.24 to 4.34 are the root-
mean-square delay spread over the distance of the first arrived path for
the omnidirectional antenna and directive antennas.

68
When an omnidirectional antenna is used at the transmitter or
receiver side, most of the channel parameters are in the region of K < 3,
σ > 5ns, Bc0.5 < 200MHz and Bc0.9 < 20MHz. The K-factors in the LOS
case are generally small because of the highly reflective environment.
Under the non line-of-sight condition, channel parameters are strongly
variant depending on the position of the receiver, due to the absence of
the direct path. From the measured data, it is found that for all the
antenna configurations, the coherence bandwidths at level 0.9 can be
related to the root mean square delay spreads, by σ Bc0.9 =0.063,
while the mean values of σ Bc0.5 are highly variant for different
configurations.
Table 4.10: RMS delay spread against distance under LOS condition
RDS(ns) Distance(m)
1.4/1.4
RDS(ns) Distance(m)
1.9/1.4
RDS(ns) Distance(m)
2.4/1.4
5 0.8 11 0.7 16 1.2
4 0.9 10 0.9 18 1.3
4 1.0 12 1.0 20 2.4
6 2.2 15 1.1 22 2.6
8 2.3 16 1.4 24 2.3
9 2.2 14 2.3 18 2.5
4 3.0 14 2.4 19 3.4
5 1.6 14 2.6 17 3.8
6 3.4 13 3.0 24 4.6
5 4.0 12 3.2 16 4.2
4 4.1 13 2.4 18 4.1
7 5.6 14 3.0 19 4.3
8 5.4 11 3.1 20 4.4
10 5.0 12 3.6 21 5.0
6 5.2 10 3.2 24 5.2
5 3.2 9 4.3 23 2.3
10 3.4 8 4.4 25 4.3
4 2.4 10 3.1 26 3.4
5 2.3 11 4.1 28 4.1
6 3.1 13 5.6 16 5.0

69
Figure 4.24: The RMS delay spread over the travel distance of the first
0 1 2 3 4 5 6
4
5
6
7
8
9
10
Travel distance of the first arrived path for omn-omn antennas(m)(1.4/1.4))
RMSdelayspread(ns)
RMS delay spread against travel distance under LOS condition

70
0 1 2 3 4 5 6
8
9
10
11
12
13
14
15
16
RMSdelayspread(ns) RMS delay spread against travel distance under LOS condition

71
arrived path of the omnidirectional antenna at 2.4/1.4).
Table 4.11: RMS delay spread against distance under NLOS condition
RDS(ns) Distance(m)
1.4/1.4
RDS(ns) Distance(m)
1.9/1.4
RDS(ns) Distance(m)
2.4/1.4
4 8.0 8 8.3 9 8.0
6 8.1 9 8.5 11 10.0
5 7.9 10 8.1 13 8.3
7 9.4 13 10.4 12 8.2
8 10.1 20 11.2 15 10.4
10 10.3 15 10.4 16 11.3
12 11.4 16 10.5 20 12.4
15 12.0 18 11.3 24 13.3
12 9.6 17 12.0 30 11.6
13 9.8 16 12.4 33 11.8
14 10.0 15 9.3 34 8.4
13 10.5 14 9.5 31 13.4
14 11.2 25 10.3 20 10.3
14 12.0 22 11.4 21 10.2
13 10.0 23 10.0 18 9.3
10 11.3 25 9.3 17 10.3
9 9.3 18 9.6 14 10.4
8 13.4 19 9.8 15 11.3
8 13.2 20 13.4 13 13.3
6 11.3 14 13.8 20 12.4
1 1.5 2 2.5 3 3.5 4 4.5 5 5.5
16
18
20
22
24
26
28
RMSdelayspread(ns)
RMS delay spread against travel distance under LOS condition

72
arrived path of the omnidirectional antenna under NLOS condition at
heights (1.4/1.4).
7 8 9 10 11 12 13 14
4
6
8
10
12
14
16
RMSdelayspread(ns) RMS delay spread against travel distance under NLOS condition

73
heights (1.9/1.4)
8 9 10 11 12 13 14
8
10
12
14
16
18
20
22
24
26
RMSdelayspread(ns)
RMS delay spread against travel distance under NLOS condition

74
heights (2.4/1.4).
Table 4.12: RMS delay spread against distance for directive antennas
RDS(ns) Distance(m)
Fan-Omn
RDS(ns) Distance(m)
Fan-Fan
RDS(ns) Distance(m)
Fan-Pen
37 1.9 1.0 1.9 1.1 1.9
38 2.0 1.2 2.0 1.2 2.0
36 2.4 1.0 2.1 1.15 2.2
32 2.3 1.2 2.3 1.15 2.3
30 2.5 2.2 2.4 1.2 2.2
31 2.6 3.0 3.1 1.1 3.4
26 2.8 1.2 3.6 1.1 3.6
24 2.9 2.0 3.5 1.2 4.2
25 3.1 1.3 3.4 1.15 3.5
10 3.3 2.0 3.2 1.1 3.6
9 3.4 1.2 4.3 1.15 4.2
6 3.5 1.0 4.5 1.1 3.5
5 3.5 1.3 4.4 0.8 3.6
6 3.6 1.0 4.6 0.9 4.3
8 4.2 1.0 5.1 0.8 4.4
7 4.3 2.0 5.3 1.0 4.3
11 4.5 1.0 5.2 1.1 4.2
10 4.6 2.2 5.3 1.0 4.1
12 5.3 1.2 3.2 0.9 5.2
22 5.2 2.0 5.4 0.8 5.3
8 9 10 11 12 13 14
5
10
15
20
25
30
35
Travel distance of the first arrived for omn-omn antennas(m)(2.4/1.4))
RMSdelayspread(ns)
RMS delay spread against travel distance under NLOS condition

75
arrived path for the Fan-Omn antennas.
1.5 2 2.5 3 3.5 4 4.5 5 5.5
5
10
15
20
25
30
35
40
Travel distance of the first arrived path for Fan-Omn antennas(m)
RMSdelayspread(ns) RMS delay spread against TX/RXdistance

76
arrived path for the Fan-Fan antennas.
1.5 2 2.5 3 3.5 4 4.5 5 5.5
5
10
15
20
25
30
35
40
Travel distance of the first arrived path for Fan-Omn antennas(m)
RMSdelayspread(ns) RMS delay spread against TX/RXdistance

77
arrived path for the Fan-Pen antennas.
Table 4.13: RMS delay spread against distance for directive antennas (35°)
RDS(ns) Distance for Fan-Fan RDS(ns) Distance for Fan-Pen
1.8 1.9 3.2 1.9
1.4 2.0 3.9 2.0
1.5 2.2 3.5 2.4
1.4 2.3 2.8 2.6
1.3 2.2 3.3 3.0
1.2 3.4 3.0 3.2
1.45 3.6 3.2 3.1
1.43 4.2 2.9 4.0
1.4 3.5 2.8 4.3
1.46 3.6 2.5 5.2
1.8 4.2 1.5 5.6
1.9 3.5 1.1 5.3
2.2 3.6 1.4 5.2
2.0 4.3 1.5 3.4
2.35 4.4 1.7 3.6
2.1 4.3 1.8 3.4
1.6 4.2 2.2 2.4
1.8 4.1 2.4 2.6
1.4 5.2 1.8 5.4
1.45 5.3 2.0 3.4
1.5 2 2.5 3 3.5 4 4.5 5 5.5
0.8
0.85
0.9
0.95
1
1.05
1.1
1.15
1.2
1.25
RMSdelayspread(ns)
RMS delay spread against TX/RX distance

78
arrived path for the Fan-Fan antennas with 35° misalignment.
1.5 2 2.5 3 3.5 4 4.5 5 5.5 6
1
1.2
1.4
1.6
1.8
2
2.2
2.4
Travel distance of the first arrived for Fan-Fan antennas(m)
RMSdelayspread(ns)
RMS delay spread against TX/RXdistance with 35(degrees) diviation

79
arrived path for the Fan-Pen antennas with 35° misalignment.
1.5 2 2.5 3 3.5 4 4.5 5 5.5 6
1
1.5
2
2.5
3
3.5
4
RMSdelayspread(ns) RMS delay spread against TX/RXdistance with 35(degrees) deviation

80
4.3 Power Delay Profile
Table 4.14: Normalized average PDP over Time delay
Normalized
Average PDP(dB)
Time (ns) for
Fan-Pen
Normalized
Average PDP(dB)
Time (ns)) for
Fan-Pen(35°)
Normalized
Average PDP(dB)
Time(ns) for
Omn-Omn
0 0 0 0 0 0
-5 3.0 -5 1 -10 2
-10 3.5 -10 2 -12 3
-12 3.6 -11 3 -13 5
-15 3.8 -11 5 -14 7
-17 4.0 -11 6 -17 8
-18 4.5 -11 12 -18 10
-19 5.0 -11 15 -19 11
-20 3.5 -11 20 -20 15
-21 7.0 -13 22 -21 17
-22 7.5 -15 23 -23 20
-25 8.0 -18 25 -25 21
-26 8.5 -23 28 -27 22
-25 8.7 -24 33 -30 24
-26 8.8 -26 37 -32 26
-25 8.9 -28 44 -35 30
-27 9.0 -30 60 -37 32
-28 10.0 -33 75 -39 37
-28 11.0 -35 80 -41 38
-30 12.0 -40 100 -45 40
Figure 4.35: The Average power delay profiles shape for Fan-Pen antennas
configuration.
0 2 4 6 8 10 12
-30
-25
-20
-15
-10
-5
0
Time delay(ns)for Fan-Pen antennas
NormalizedaveragePDP(dB)

81
Figure 4.36: The Average power delay profiles shape for Fan-Pen antennas
with 35° misalignment configuration.
0 10 20 30 40 50 60 70 80 90 100
-40
-35
-30
-25
-20
-15
-10
-5
0
Time delay(ns)for Fan-Pen 35(degrees)misalignment

82
Figure 4.37: The Average power delay profiles shape for Omn-Omn
configuration.
0 5 10 15 20 25 30 35 40
-45
-40
-35
-30
-25
-20
-15
-10
-5
0
Time delay(ns)for omn-omn antennas(1.4/1.4))

83
Taking the average over all the measured profiles for each
configuration, each individual profile is normalized by its total received
power. From these averages, the following can be observed as shown in
the figures above.
(1) Figure 4.37 shows that when the transmitter and receiver beams are
aligned to each other under the line-of-sight condition, the normalized
average delay profile consists of a direct ray and an exponentially
decaying part.
(2) Under the non line-of-sight condition, the average delay profile will be
exponentially decaying without a constant part, due to the lower
dependency of antenna pattern and misalignment.
(3) Figure 4.36 shows that when the transmitter and receiver beams are
strongly misaligned and out of sight to each other, a constant level part
will appear before an exponentially decaying part. It can be observed
that, the average delay profile can be regarded as a function of excess
delay that consists of a direct part, a constant part and a linear
decaying part.

85
4.4 Maximum Excess Delays and Number of Multipath Component
For the various measurement configurations, the multipath
components are recognized from the local peaks in the profile. Within
the dynamic range of 30dB of power delay profile, the maximum excess
max and the number of multipath components N are determined.
max are distributed within 10 to 170ns and so is the
values of N within 3 to 100, depending on the channel configurations.
For all the measured profiles, the number of paths per nanosecond,
max, has a mean value of 0.3 with a standard deviation of 0.06
showing that there is minimum delay using the 60GHz band.

86
CHAPTER 5
CONCLUSION
In this report, the time dispersion and frequency selectivity of
millimeter wave propagation at 60GHz channels with various antenna
configurations were based on extensive channel measurements in Line-
of-sight and non line-of-sight environments. Statistical channel
parameters were obtained from the measurement and compared, which
showed that the power level of the directive antenna configuration is
much higher and the loss exponents are much smaller than the free-
space for omn-omn configuration. The measurement of the width of the
delay power spectrum known as RMS delay spread and power delay
profiles were retrieved based on a simple profile model.
5.1 Conclusion
For the considered environments and antenna configurations, the
following conclusions can be drawn.
(1) The transmitter and receiver antenna beams have to be properly
aligned within the sight of each other, else the beam-pointing errors
will cause an enormous drop in the channel quality. The wider beam
antennas are less sensitive for beam-pointing errors, which indicates
that a proper beamwidth has to be designed in practice.

87
(2) To increase the signal coverage and performance in the NLOS area, it
is preferable to apply directive antennas.
(3) When an omnidirectional antenna is used at the transmitter or
receiver side in a LOS case, the channel parameters are generally small
because of the reflective environment.
(4) The measurement results have shown that the use of high gain
antenna can significantly reduce the delay spread of the distributed
wireless communication system channel when the transmitter and
receiver antennas are aligned.
5.2 Recommendation
Based on the above analysis and results obtained, it can be
observed that millimeter wave propagation has the potentials to provide
the next generation multigigabit wireless communication system.
Further research work could be aimed at understanding the link
budget, the effects of rain-induced bistatic scattering, and the effects of
atmospheric oxygen, humidity and fog in millimeter wave propagation.

88
REFERENCES
Balanis C.A. (1997): Antenna Theory: Analysis and Design, John Wiley
& Sons, New York, NY, USA, 2nd edition.
Chong C.C. and Yong S.K. (2007): An overview of multigigabit wireless
through millimeter wave technology: potentials and technical
challenges, EURASIP Journal, 2007 (2): 3 – 6.
Kvicera V. and Grabner M. (2007): Rain Attenuation at 58 GHz:
Prediction versus Long-Term Trial Results, EURASIP Journal, 2007 (6):
3-6.
Lim C.P, Lee, M., Burkholder R.J., Volakis J.L., Marhefka, R.J. (2007):
60 GHz indoor propagation studies for wireless communication based
on Ray-tracing method, EURASIP Journal, 2007 (4): 2 – 3.
Mohammadi A., Shayegh Abdipour, A. and Mirzavand R. (2007): Direct
Conversion EHM transceivers Design for millimeter – wave wireless
Applications, EURASIP Journal, 2007(9): 1-6.
Moraitis N. and Constantinou P. (2004): Indoor Channel measurements
and characterization of 60GHz for wireless local area network
applications, IEEE Transactions on Antennas and propagation, 47(12):
3180 – 3189.
Muqaibel A.H. (2003): Characterization of ultra widespread
communication channels, Ph.D dissertation, Virginia polytechnic
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Nan G., Qui, R.C., Mo S.S. and Yakahashi K. (2007): 60GHz
Milliimeter-wave Radio: Principle, Technology, and new Results,
EURASIP Journal, 2007(3): 3-5.
Pozar, D.M. (2001): Microwave and RF Design of wireless systems,
John wiley and sons, New York: 324 – 327.
Sadiku, M.N.O. (2002): Optical and wireless communications, CRC
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Shidong Zhou, Ming Zhao, Xibin Xu, Jing Wang and Yan Yao. (2003):
Distributed wireless communication system: A new Architecture for

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future public wireless access, IEEE Communications magazine, E03-R:
108 – 113.
Witrisal, K. Kim, Y.H. and Prasad, R. (1998): RMS Delay Spread
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IEE Electronic Letters, 34 (20): 1918 – 1919
Yang, H. Smulders, P.F.M. and Herben, M.H.A.J. (2007): Channel
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90
APPENDICES
A1: MATLAB GRAPH PLOTTING SOURCE CODE
FIRST GRAPH
%('Received Power (dBm) VS Travel distance of the first arrived Path')
A = [-48 -48.5 -50 -50 -51 -52 -51 -53 -53 -54 -54 -55 -55 -55 -56 -56 -56 -57 -
58 -60 -61 -62];%Received Power (dBm)
B = [0.9 0.1 1.2 1.3 1.5 1.53 1.8 2.2 2.3 2.1 2.7 2.0 2.8 3.0 4.4 1.8 3.2 2.6 1.4
4.2 1.8 3.7];%Travel distance of the arrived path(m)
scatter(B,A,'*')
xlabel('Travel distance of the first arrived path for omn-omm (m)(1.4/1/4')
ylabel('Received Power(dBm)')
title('received power(dBm)against travel distance')
SECOND GRAPH
C = [-67 -68 -64.4 -65.5 -66 -64 -64 -63 -66 -67 -67.5 -65 -66 -66 -66.5 -65 -70
-65 -68 -65];%Received Power (dBm)
D = [0.9 1.1 1.2 1.5 1.45 1.8 2.1 2.0 1.9 2.1 2.2 2.7 2.9 3.0 3.3 3.2 3.5 3.5 5.3
2.2];%Travel distance of the arrived path(m)
scatter(D,C,'*')
xlabel('Travel distance of the first arrived path for omn-omm(1.9/1.4)')
title('Received power (dBm) against travel distance under LOS condition')
THIRD GRAPH
E = [-70 -72 -72.5 -74 -75 -71 -71.5 -71 -73 -71 -71 -69 -72 -71 -75 -75 -74 -74
-74 -74];%Received Power (dBm)
F = [1.2 1.3 1.2 1.3 1.8 2.0 2.1 2.0 3.2 3.4 3.6 3.9 4.0 4.1 3.2 3.3 5.4 5.5 5.6
scatter(F,E,'*')
title('Received power (dBm) against Travel distance (m) under LOS condition')
FOURTH GRAPH
G = [-56 -60 -63 -66 -60 -64 -64 -67 -66 -67 -68 -72 -73 -75 -72 -77 -71 -63 -67
-67];%Received Power (dBm)
H = [8.5 8.1 8.0 8.0 8.2 8.5 8.7 8.5 9.8 9.3 9.1 9.5 9.4 9.2 12.5 13.5 12.0 11.0
10.5 11.5];%Travel distance of the arrived path(m)
scatter(H,G,'*')
title('Received power (dBm) against travel distance under NLOS condition')
FIFTH GRAPH
I = [-66 -66 -69 -70 -71 -71 -72 -71 -68 -70 -71 -75 -75 -80 -76 -83 -80 -83 -73
J = [8 8.5 8.2 9.0 9.1 8.9 9.0 8.9 11.5 11.3 11.5 13.3 12 13.6 13 11.5 12 13 10.5
11];%Travel distance of the arrived path(m)
scatter(J,I,'*')

91
SIXTH GRAPH
K = [-70 -73 -70 -83 -82 -83 -83 -84 -84 -84 -83 -76 -74 -72 -80 -81 -80 -79 -73
L = [8 7.8 7.8 10 9.5 10.5 11 12 12.3 12.8 13 10 10.5 11 13 12.6 13.5 13 11.5
scatter(L,K,'*')
SEVENTH GRAPH
M = [-30 -33 -35 -37 -40 -43 -45 -47 -50 -53 -55 -57 -60 -67 -65 -67 -70 -73 ];
%Received Power (dBm)
N = [0.3 0.3 0.4 0.4 0.5 0.8 0.9 1.2 1.3 1.5 2.0 2.8 3.5 4.8 6 7 10 14]; %Travel
distance of the arrived path(m)
scatter(N,M,'*')
xlabel('Travel distance of the first path.')
title('Received power (dBm) against travel distance under free space')
EIGHT GRAPH
% %Received Power (dB)and Tx-Rx distance (m)
A = [-65 -66 -65 -63 -60 -62 -64 -55 -60 -53 -56 -58 -57 -60 -57 -58 -59 -58 -57
-59];%Received Power(dBm)
B = [1.9 2 2.2 2.4 2.5 2.3 2.5 4.3 3 3.3 3.4 3.5 4 5.7 4.8 5.0 5.2 4.3 4.2
5.2];%Fan-omn(m)
scatter(B,A,'+')
xlabel('Travel distance of the first arrived path for the directive antenna(m)')
title('Received power against TX/RX distance for Fan-Omn antennas')
NINETH GRAPH
C = [-49 -46 -47 -48 -47 -46 -45 -44 -43 -43 -44 -42 -42 -42 -42 -42 -41 -41 -41
-42 -42];%Received Power(dBm)
D = [1.9 2.0 2.1 2.2 2.3 2.5 2.5 2.6 2.7 2.8 2.9 3.0 3.1 3.2 3.3 3.5 3.6 3.8 4.0
4.2 4.3];%Fan-omn(m)
scatter(D,C,'+')
title('Received power against TX/RX distance for Fan-Fan antennas')
TENTH GRAPH
E = [-40 -39 -40 -41 -41 -41 -39 -38 -37 -36 -35 -34 -34 -34 -34 -34 -33 -33 -34
F = [1.9 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3.0 3.1 3.2 3.3 3.4 3.5 3.6 3.7 3.8
3.9];%Fan-pen(m)
scatter(F,E,'+')
title('Received power against TX/RX distance for Fan-Pen antennas')
ELEVENTH GRAPH
G = [-53 -51 -50 -53 -53 -54 -53 -54 -50 -49 -48 -48 -48 -49 -48 -49 -47 -47 -47
H = [1.9 2.0 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3.1 3.2 3.3 3.4 3.5 3.6 3.7 4.2
4.4];%Fan-Fan 35(degree)deviation
scatter(H,G,'+')
xlabel('Travel distance of the first arrived path for directive antenna(m)')

92
title('Received power against TX/RX distance for Fan-Fan 35(degree) deviation')
TWELVETH GRAPH
I = [-66 -67 -67 -68 -65 -64 -64 -65 -65 -65 -65 -66 -66 -67 -65 -66 -66 -65 -66
J = [1.9 2.0 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.9 3.0 3.2 3.3 3.5 3.6 3.7 4.2 4.3 4.4
4.5];%Fan-Pen 35(degree)deviation
scatter(J,I,'+')
xlabel('Travel distance of the first arrived path for directive antenna(m)')
title('Received power against TX/RX distance for Fan-Pen 35(degree) deviation')
THIRTEENTH GRAPH
%Plot K-factor against travel distance of the first arrived Path
%dat gotten from experiment performed
K1 = [2.1 1.2 1.8 0.4 1.0 1.1 1.2 1.4 1.6 1.8 0.9 1.0 1.0 1.2 1.3 1.4 1.6 1.5 1.8
1.3];%K-factor
Los = [0.8 1 1 2 2.3 2.4 3 4.2 4.1 4.3 4.2 4.2 4.5 4.2 3.3 3.4 3.2 1.0 3.4
5.0];%Los omn-omn (1.4/1.4)
scatter(Los,K1,'*')
ylabel('K-factor')
xlabel('Travel distance of the first arrived path for omnidirectional
antenna(m)(1.4/1.4)')
title('K-factor against travel distance under LOS condition')
FOURTEENTH GRAPH
K2 = [0.3 0.2 0.4 0.6 1.8 1.7 0.4 0.5 0.5 0.7 0.5 0.3 0.5 0.1 1 1.1 1.0 0.7 0.9
0.6];%K-factor
Los2 = [0.9 1.0 0.8 1.3 1.2 1.8 2.1 2.0 2.1 3.0 3.3 3.4 4.2 4.5 4.3 4.2 4.3 4.2
5.0 5.2];%Los omn-omn (1.9/1.4)
scatter(Los2,K2,'*')
ylabel('K-factor')
xlabel('Travel distance of the first arrived path for omnidirectional
antenna(m)(1.9/1.4)')
FIFTEENTH GRAPH
K3 =[0.1 0.3 0.5 0.2 0.1 0.4 0.5 0.3 0.1 0.2 0.4 1.0 0.9 0.7 1.0 0.8 0.4 0.1 0.2
0.5];%K-factor
Los3 = [1.2 1.3 1.0 1.8 1.9 2.1 2.2 2.3 2.5 2.1 2.2 2.4 2.3 2.5 3.4 3.3 3.2 4.3
5.2 5.3];%Los omn-omn (2.4/1.4)
ylabel('K-factor')
xlabel('Travel distance of the first arrived path for omn-omn(m)(2.4/1.4)')
SIXTEENTH GRAPH
%data values for NLos omn-omn gotten from experiment
K4 = [4.8 2.0 2.1 1.9 1.5 1.8 1.7 1.9 1.5 1.8 0.1 0.4 0.3 0.2 0.5 0.4 0.3 0.2 0.3
1.8];%K-factor
Los4 = [8 7.8 8.4 8.2 8.1 8.5 8.6 9.2 9.3 9.0 10.4 10.3 11.2 12.3 11.4 11.4 11.6
12.4 13.3 13.5];%NLos omn-omn (1.4/1.4)
ylabel('K-factor')
xlabel('Travel distance of the first arrived path for omn-omn
antennas(m)(1.4/1.4)')
title('k-factor against travel distance under NLOS condition')
SEVENTEENTH GRAPH

93
K5 = [7.4 7.2 8.9 4.9 2.1 2.3 1.8 1.9 2.0 1.5 1.3 2.1 2.0 2.3 2.4 2.6 2.8 1.0 1.1
1.3];%K-factor
Los5 = [8.9 8.1 8.7 9.1 9.3 9.4 10.4 11.0 10.8 10.7 11.4 12.4 12.5 13.0 9.4 9.6
12.4 13.0 13.3 13.3];%NLos omn-omn (1.9/1.4)
ylabel('K-factor')
title('K-factor against travel distance under NLOS condition')
EIGHTEENTH GRAPH
K6 = [5.3 0.5 1.2 0.3 0.4 0.3 0.2 0.3 0.4 0.3 0.5 1.2 1.3 1.5 0.3 0.6 1.3 2.1
2.3 3.5];%K-factor
Los6 = [8.3 8.6 9.1 9.3 8.4 10.3 10.6 11.0 10.4 8.4 8.6 10.4 13.0 13.3 12.1 12.3
8.6 8.4 9.3 9.4];%NLos omn-omn (2.4/1.4)
ylabel('K-factor')
title('K-factor against travel distance under NLOS condition')
NINETEENTH GRAPH
%plot of K-factor against Tx-Rx distance(m)
K1 = [0.8 1.0 1.0 1.2 1.5 1.4 1.6 1.8 2.1 2.3 1.3 1.5 5.0 4.3 4.8 3.0 3.5 3.6 4.0
2.0];%K-factor
F1 = [1.9 2.0 2.2 2.3 2.5 3.0 2.8 3.4 3.6 3.7 3.5 3.6 4.0 4.2 4.3 4.2 4.6 5.0 5.4
5.3];%Fan-omn
scatter(F1,K1,'*')
xlabel('Travel distance of the first arrived path for Fan-omn antennas(m)')
ylabel('K-factor')
title('K-factor against TX/RX distance')
TWENTIETH GRAPH
K2 = [10.0 11.0 10 13 12 14 15 14 16 12 11 10 9 8 7 10 12 13 11 13];%K-factor
F2 = [1.9 2 2.3 2.3 3.4 3.0 3.1 3.2 3.4 4 4.2 4.4 4.3 5.0 5.3 5.4 5.6 4.3 4.2
4.1];%Fan-omn
scatter(F2,K2,'*')
xlabel('Travel distance of the first arrived path for Fan-Fan antennas(m)')
ylabel('K-factor')
TWENTY-FIRST GRAPH
K3 = [11 12 15 18 16 20 21 23 36 20 21 18 19 24 16 12 11 10 13 14];%K-factor
F3 = [1.9 2 2.2 2.4 3.4 3.2 3.3 4.6 4.2 4.8 3.4 5.3 5.2 4.8 4.6 3.6 4.8 5 5.3 5.2
];%Fan-omn
scatter(F3,K3,'*')
xlabel('Travel distance of the first arrived path for Fan-Pen antennas(m)')
ylabel('K-factor')
TWENTY-SECOND GRAPH
%this the datas for the anagular deviation of 35degree
K4 = [8 10 9 8 10 7 8 10 6 7 8 10 11 12 11 6 7 8 10 20 ];%K-factor
F4 = [1.9 2 2.2 2.3 2.4 4 4.2 3.6 4.1 4.3 3.6 3.2 3.3 3.4 4.2 4.3 5 5.6 5.7
5.2];%Fan-fan 35degree deviation
scatter(F4,K4,'*')
ylabel('K-factor')
title(' K-factor against TX/RX distance with 35(degrees) deviation')

94
TWENTY-THIRD GRAPH
K5 = [4 1 2 4 5 6 1 3 4 5 7 2 4 6 3 2 5 4 3 4 ];%K-factor
F5 = [1.9 2.0 2.3 2.4 2 3 3.4 4.6 4.1 4.3 5 5.2 5.3 4.3 4.4 4.6 4.1 4.3 4.2
5];%Fan-pen 35degree deviation
scatter(F3,K3,'*')
ylabel('K-factor')
title('K-factor against TX/RX distance with 35(degrees) diviation')
TWENTY-FOURTH GRAPH
%Plot Rms delay spread against ttavel distance of the first arrived Path
R1 = [5 4 4 6 8 9 4 5 6 5 4 7 8 10 6 5 10 4 5 6 ];%RDS(ns)
Los1 = [0.8 0.9 1 2.2 2.3 2.2 3 1.6 3.4 4 4.1 5.6 5.4 5 5.2 3.2 3.4 2.4 2.3
3.1];%Los (omn-omn(1.4/1.4)
scatter(Los1,R1,'*')
antennas(m)(1.4/1.4))')
ylabel('RMS delay spread(ns)')
title('RMS delay spread against travel distance under LOS condition')
TWENTY-FIFTH GRAPH
R2 = [11 10 12 15 16 14 14 14 13 12 13 14 11 12 10 9 8 10 11 13];%RDS(ns)
Los2 = [0.7 0.9 1 1.1 1.4 2.3 2.4 2.6 3 3.2 2.4 3 3.1 3.6 3.2 4.3 4.4 3.1 4.1
5.6];%%Los (omn-omn(1.9/1.4))
antennas(m)(1.9/1.4))')
TWENTY-SIXTH GRAPH
R3 = [16 18 20 22 24 18 19 17 24 16 18 19 20 21 24 23 25 26 28 16];%RDS(ns)
Los3 = [1.2 1.3 2.4 2.6 2.3 2.5 3.4 3.8 4.6 4.2 4.1 4.3 4.4 5 5.2 2.3 4.3 3.4 4.1
5];%Los (omn-omn(2.4/1.4))
xlabel(' Travel distance of the first arrived path for omn-omn
antennas(m)(2.4/1.4))')
TWENTY-SEVENTH GRAPH
R4 = [4 6 5 7 8 10 12 15 12 13 14 13 14 14 13 10 9 8 8 6];%RDS(ns)
Los4 = [8 8.1 7.9 9.4 10.1 10.3 11.4 12.0 9.6 9.8 10.0 10.5 11.2 12.0 10.0 11.3
9.3 13.4 13.2 11.3];%NLos (omn-omn(1.4/1.4))
antennas(m)(1.4/1.4))')
title('RMS delay spread against travel distance under NLOS condition')
TWENTY-EIGHT GRAPH
R5 = [8 9 10 13 20 15 16 18 17 16 15 14 25 22 23 25 18 19 20 14];
Los5 = [8.3 8.5 8.1 10.4 11.2 10.4 10.5 11.3 12 12.4 9.3 9.5 10.3 11.4 10 9.3 9.6
9.8 13.4 13.8];
antennas(m)(1.9/1.4))')

95
TWENTY-NINETH GRAPH
R6 = [9 11 13 12 15 16 20 24 30 33 34 31 20 21 18 17 14 15 13 20];
Los6 = [8 10 8.3 8.2 10.4 11.3 12.4 13.3 11.6 11.8 8.4 13.4 10.3 10.2 9.3 10.3
10.4 11.3 13.3 12.4];
xlabel('Travel distance of the first arrived for omn-omn antennas(m)(2.4/1.4))')
THIRTIETTH GRAPH
%RSM delay spread (ns) against Tx-Rx distance(m)
A = [37 38 36 32 30 31 26 24 25 10 9 6 5 6 8 7 11 10 12 22];
B = [1.9 2 2.4 2.3 2.5 2.6 2.8 2.9 3.1 3.3 3.4 3.5 3.5 3.6 4.2 4.3 4.5 4.6 5.3
5.2];
scatter(B,A,'*')
xlabel('Travel distance of the first arrived path for Fan-Omn antennas(m)')
title('RMS delay spread against TX/RX distance')
THIRTY-FIRST GRAPH
R2 = [1 1.2 1 1.2 2.2 3 1.2 2 1.3 2 1.2 1 1.3 1 1 2 1 2.2 1.2 2 ];
F2 = [1.9 2 2.1 2.3 2.4 3.1 3.6 3.5 3.4 3.2 4.3 4.5 4.4 4.6 5.1 5.3 5.2 5.3 3.2
5.4];
scatter(F2,R2,'*')
THIRTY-SECOND GRAPH
R3 = [1.1 1.2 1.15 1.15 1.2 1.1 1.1 1.2 1.15 1.1 1.15 1.1 0.8 0.9 0.8 1.0 1.1 1.0
0.9 0.8];
F3 = [1.9 2 2.2 2.3 2.2 3.4 3.6 4.2 3.5 3.6 4.2 3.5 3.6 4.3 4.4 4.3 4.2 4.1 5.2
5.3 ];
scatter(F3,R3,'*')
THIRTY-THIRD GRAPH
R4 = [1.8 1.4 1.5 1.4 1.3 1.2 1.45 1.43 1.42 1.46 1.8 1.9 2.2 2 2.35 2.1 1.6 1.8
1.4 1.45];
F4 = [1.9 2.0 2.2 2 1.9 2.4 2.3 4.6 4.3 3.4 3.2 3.3 3.2 3.4 5.6 5.4 5.2 4.6 4.3
4.6];
scatter(F4,R4,'*')
xlabel('Travel distance of the first arrived for Fan-Fan antennas(m)')
title('RMS delay spread against TX/RX distance with 35(degrees) diviation')
THIRTY-FOURTH GRAPH
R5 = [3.2 3.9 3.5 2.8 3.3 3.0 3.2 2.9 2.8 2.5 1.5 1.1 1.4 1.5 1.7 1.8 2.2 2.4 1.8
2.0];
F5 = [1.9 2 2.4 2.6 3 3.2 3.1 4 4.3 5.2 5.6 5.3 5.2 3.4 3.6 3.4 2.4 2.6 5.4 3.4];
scatter(F5,R5,'*')
title('RMS delay spread against TX/RX distance with 35(degrees) deviation')

96
THIRTY-FIFTH GRAPH
%Normalised average PDP
P2 = [0 -5 -10 -12 -15 -17 -18 -19 -20 -21 -22 -25 -26 -25 -26 -25 -27 -28 -28 -
30];
F2 = [0 3 3.5 3.6 3.8 4 4.5 5 3.5 7 7.5 8 8.5 8.7 8.8 8.9 9 10 11 12];
scatter(F2,P2,'*')
xlabel('Time delay(ns)for Fan-Pen antennas')
ylabel('Normalized average PDP(dB)')
grid on
THIRTY-SIXTH GRAPH
P2i = [0 -5 -10 -11 -11 -11 -11 -11 -11 -13 -15 -18 -23 -24 -26 -28 -30 -33 -35 -
40];
F2i = [0 1 2 3 5 6 12 15 20 22 23 25 28 33 37 44 60 75 80 100];
scatter(F2i,P2i,'*')
xlabel('Time delay(ns)for Fan-Pen 35(degrees)misalignment')
grid on
THIRTY-SEVENTH GRAPH
P2i = [0 -10 -12 -13 -14 -17 -18 -19 -20 -21 -23 -25 -27 -30 -32 -35 -37 -39 -41
-45];
F2i = [0 2 3 5 7 8 10 11 15 17 20 21 22 24 26 30 32 37 38 40];
scatter(F2i,P2i,'*')
xlabel('Time delay(ns)for omn-omn antennas(1.4/1.4))')
grid on
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